View AAT1153IDE-06-T1_3235597.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 1 www.analogictech.com general description the aat1153 switchreg? is a 1.2mhz constant fre- quency current mode pwm step-down converter. it is ideal for portable equipment requiring very high current up to 2a from single-cell lithium-ion batteries while still achieving over 90% efficiency during peak load condi- tions. the aat1153 also can run at 100% duty cycle for low dropout operation, extending battery life in portable systems while light load operation provides very low output ripple for noise sensitive applications. the aat1153 can supply up to 2a output load current from a 2.5v to 5.5v input voltage and the output voltage can be regulated as low as 0.6v. the high switching fre- quency minimizes the size of external components while keeping switching losses low. the internal slope compen- sation setting allows the device to operate with smaller inductor values to optimize size and provide efficient operation. the aat1153 is available in adjustable (0.6v to v in ) and fixed (1.8v) output voltage versions. the device is avail- able in a pb-free, 3mm x 3mm 10-lead tdfn package and is rated over the -40c to +85c temperature range. features ? input voltage range: 2.5v to 5.5v ? output voltages from 0.6v to v in ? 2a output current ? high efficiency: up to 95% ? 1.2mhz constant switching frequency ? low r ds(on) internal switches: 0.15 ? allows use of ceramic capacitors ? current mode operation for excellent line and load transient response ? short-circuit and thermal fault protection ? soft start ? low dropout operation: 100% duty cycle ? low shutdown current: i shutdown < 1 a ? tdfn33-10 package ? -40c to +85c temperature range applications ? cellular phones ? digital cameras ? dsp core supplies ? pdas ? portable instruments ? smart phones typical application pgnd pgnd lx lx en in ain agnd out aat1153-1.8 c1 22f v in 2.5v-5.5v l1 2.2h c2 22f v out 1.8v, 2a 1 2 3 4 5 7 8 9 10 agnd 6
aat1153 2a step-down converter product datasheet 2 1153.2007.11.1.1 www.analogictech.com aat1153 2a step-down converter product datasheet 2 1153.2007.11.1.1 www.analogictech.com pin descriptions pin # symbol function 1en enable pin. active high. in shutdown, all functions are disabled drawing <1 a supply current. do not leave en oating. 2 in power supply input pin. must be closely decoupled to agnd with a 2.2 f or greater ceramic capacitor. 3 ain analog supply input pin. provides bias for internal circuitry. 4, 6 agnd analog ground pin 5 fb/out fb pin (aat1153ide-0.6): adjustable version feedback input. connect fb to the center point of the external resistor divider. the feedback threshold voltage is 0.6v. out pin (aat1153ide-1.8): fixed version feedback input. connect out to the output voltage, vout. 7, 8 lx switching node pin. connect the output inductor to this pin. 9, 10 pgnd power ground pin ep power ground exposed pad. must be connected to bare copper ground plane. pin configuration tdfn-10 (top view) ain fb/out agnd en in lx agnd lx pgnd pgnd 3 4 5 1 2 8 7 6 10 9 1. fb pin for the adjustable voltage version (aat1153ide-0.6), out pin for the fixed voltage version (aat1153ide-1.8).
aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 3 www.analogictech.com absolute maximum ratings 1 symbol description value units in, ain input supply voltages -0.3 to 6.0 v v fb , v lx fb, lx voltages -0.3 to v in + 0.3 v v en en voltage -0.3 to v in + 0.3 v pgnd, agnd ground voltages -0.3 to 6.0 v t a operating temperature range -40 to +85 c t storage storage temperature -65 to 150 c t lead lead temperature (soldering, 10s) 300 c thermal information 2 symbol description value units ja thermal resistance 3 45 c/w p d maximum thermal dissipation at t a = 25c 2.2 w 1. absolute maximum ratings are those values beyond which the life of a device may be impaired. 2. t j is calculated from the ambient temperature t a and power dissipation p d according to the following formula: t j = t a + p d x ja . 3. thermal resistance is specified with approximately 1 square inch of 1 oz. copper.
aat1153 2a step-down converter product datasheet 4 1153.2007.11.1.1 www.analogictech.com aat1153 2a step-down converter product datasheet 4 1153.2007.11.1.1 www.analogictech.com electrical characteristics 1 v in = 3.6v, t a = -40c to +85c unless otherwise noted; typical values are t a = 25c. symbol description conditions min typ max units v in input voltage range 2 2.5 5.5 v v out output voltage range 0.6 v in v i q input dc supply current active mode: v fb = 0.5v 300 500 a shutdown mode: v en = 0v, v ain = 5.5v 0.1 1 a i fb feedback input bias current v fb = 0.65v 30 na v fb regulated feedback voltage 3 t a = 25c 0.5880 0.6000 0.6120 v 0c t a 85c 0.5865 0.6000 0.6135 -40c t a 85c 0.5850 0.6000 0.6150 v linereg / v in line regulation v in = 2.5v to 5.5v, i out = 10ma 0.10 0.20 %/v v loadreg / i out load regulation i out = 10ma to 2000ma 0.20 %/a v fb output voltage accuracy v in = 2.5 to 5.5v, i out = 10 to 2000ma -3 +3 % v out f osc oscillator frequency v fb = 0.6v 0.96 1.2 1.44 mhz t s startup time from enable to output regulation 1.3 ms t sd over-temperature shutdown threshold 170 c t hys over-temperature shutdown hysteresis 10 c i lim peak switch current 2.5 3.5 a r ds(on) p-ch mosfet v in = 3.6v 135 200 m n-ch mosfet v in = 3.6v 95 150 v en(l) enable threshold low 0.3 v v en(h) enable threshold high 1.5 v i en input low current v in = v en = 5.5v -1.0 1.0 a 1. the aat1153 is guaranteed to meet performance specifications over the -40c to +85c operating temperature range and is assu red by design, characterization, and correla- tion with statistical process controls. 2. v in should be not less than v out + v dropout , where v dropout = i out x (r ds(on)pmos + esr inductor ), typically v dropout = 0.3v. 3. the regulated feedback voltage is tested in an internal test mode that connects v fb to the output of the error amplifier.
aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 5 www.analogictech.com aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 5 www.analogictech.com typical characteristics efficiency vs. output current (v out = 3.3v, t a = 25c, l = 2.2h, c in = c out = 22f) output current (ma) efficiency (%) 0 10 20 30 40 50 60 70 80 90 100 0.1 1 10 100 1000 1000 0 v in = 3.7v v in = 4.2v v in = 5.0v v in = 5.5v dc regulation (v out = 3.3v, t a = 25c, l = 2.2h, c in = c out = 22f) output current (ma) output voltage (v) 3.201 3.234 3.267 3.300 3.333 3.366 3.399 0 200 400 600 800 1000 1200 1400 1600 1800 2000 v in = 5.5v v in = 5.0v v in = 3.7v v in = 4.2v efficiency vs. output current (v out = 1.8v, t a = 25c, l = 2.2h, c in = c out = 22f) output current (ma) efficiency (%) 0 10 20 30 40 50 60 70 80 90 100 0.1 1 10 100 1000 10000 v in = 5.5v v in = 5.0v v in = 4.2v v in = 3.6v v in = 2.5v dc regulation (v out = 1.8v, t a = 25c, l = 2.2h, c in = c out = 22f) output current (ma) output voltage (v) 1.746 1.764 1.782 1.800 1.818 1.836 1.854 0 200 400 600 800 1000 1200 1400 1600 1800 2000 v in = 5.5v v in = 5.0v v in = 4.2v v in = 3.6v v in = 2.5v efficiency vs. output current (v out = 1.5v, t a = 25c, l = 2.2h, c in = c out = 22f) output current (ma) efficiency (%) 0 10 20 30 40 50 60 70 80 90 100 0.1 1 10 100 1000 10000 v in = 5.5v v in = 5.0v v in = 4.2v v in = 3.6v v in = 2.5v dc regulation (v out = 1.5v, t a = 25c, l = 2.2h, c in = c out = 22f) output current (ma) output voltage (v) 1.455 1.470 1.485 1.500 1.515 1.530 1.545 0 200 400 600 800 1000 1200 1400 1600 1800 2000 v in = 5.5v v in = 5.0v v in = 4.2v v in = 3.6v v in = 2.5v
aat1153 2a step-down converter product datasheet 6 1153.2007.11.1.1 www.analogictech.com aat1153 2a step-down converter product datasheet 6 1153.2007.11.1.1 www.analogictech.com typical characteristics efficiency vs. output current (v out = 1.2v, t a = 25c, l = 2.2h, c in = c out = 22f) output current (ma) efficiency (%) 0 10 20 30 40 50 60 70 80 90 100 0.1 1 10 100 1000 10000 v in = 5.5v v in = 4.2v v in = 3.6v v in = 2.5v v in = 5.0v dc regulation (v out = 1.2v, t a = 25c, l = 2.2h, c in = c out = 22f) output current (ma) output voltage (v) 1.164 1.176 1.188 1.200 1.212 1.224 1.236 0 200 400 600 800 1000 1200 1400 1600 1800 2000 v in = 5.5v v in = 5.0v v in = 4.2v v in = 2.5v v in = 3.6v quiescent current vs. input voltage (t a = 25c, l = 2.2h, c in = c out = 22f) input voltage (v) input current (ma) 0.20 0.22 0.24 0.26 0.28 0.30 0.32 0.34 0.36 0.38 2.5 3.0 3.5 4.0 4.5 5.0 5.5 v out = 3.3v v out = 1.8v quiescent current vs. temperature (l = 2.2h, c in = c out = 22f) temperature (c) quiescent current (a) 200 250 300 350 400 -40 -20 0 20 40 60 80 100 v in = 4.2v v out = 3.3v v in = 3.6v v out = 1.8v line regulation (v out = 1.8v, l = 2.2h, c in = c out = 22f) input voltage (v) accuracy (%) -0.40 -0.20 0.00 0.20 0.40 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6. 0 i out = 2a i out = 1.5a i out = 1a i out = 1ma i out = 600ma
aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 7 www.analogictech.com aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 7 www.analogictech.com typical characteristics p-channel r ds(on) vs. input voltage input voltage (v) r ds(on)_p (m ) 80 100 120 140 160 180 200 2.5 3 3.5 4 4.5 5 5.5 25c -40c 85c n-channel r ds(on) vs. input voltage input voltage (v) r ds(on)_n (m ) 50 70 90 110 130 150 2.5 3 3.5 4 4.5 5 5.5 85c 25c -40c switching frequency vs. temperature (v in = 3.6v; v out = 1.8v) temperature (c) switching frequency (mhz) 1.0 1.1 1.2 1.3 1.4 -40 -20 0 20 40 60 80 10 0 reference voltage vs. temperature (v in = 3.6v) temperature (c) reference voltage (v) 0.591 0.593 0.595 0.597 0.599 0.601 0.603 0.605 0.607 0.609 -40 -20 0 20 40 60 80 100 soft start (v in = 3.6v; v out = 1.8v; i out = 2a; c ff = 22pf) time (400s/div) enable voltage (top) (v) output voltage (middle) (v) input current (bottom) (a) -2 0 2 4 6 -0.2 0.2 0.6 1.0 1.4 load transient response (v in = 3.6v; v out = 1.8v; l = 2.2h; c in = c out = 22f) time (400s/div) output voltage (top) (v) output current (bottom) (a) 1.6 1.8 2.0 2.2 -0.2 0.2 0.6 1.0 1.4 1.8 2.2 2.6 2a 200ma
aat1153 2a step-down converter product datasheet 8 1153.2007.11.1.1 www.analogictech.com aat1153 2a step-down converter product datasheet 8 1153.2007.11.1.1 www.analogictech.com typical characteristics output ripple (v in = 3.6v; v out = 1.8v; i out = 0a; l = 2.2h) time (100s/div) output voltage (top) (v) inductor current (bottom) (a) 1.79 1.80 1.81 1.82 -0.1 0.0 0.1 0.2 0.3 output ripple (v in = 3.6v; v out = 1.8v; i out = 2a; l = 2.2h) time (400ns/div) output voltage (top) (v) inductor current (bottom) (a) 1.79 1.80 1.81 1.82 1.5 1.7 1.9 2.1 2.3 2.5
aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 9 www.analogictech.com functional description the aat1153 is a high output current monolithic switch- mode step-down dc-dc converter. the device operates at a fixed 1.2mhz switching frequency, and uses a slope compensated current mode architecture. this step-down dc-dc converter can supply up to 2a output current at v in = 3v and has an input voltage range from 2.5v to 5.5v. it minimizes external component size and opti- mizes efficiency at the heavy load range. the slope com- pensation allows the device to remain stable over a wider range of inductor values so that smaller values (1 h to 4.7 h) with lower dcr can be used to achieve higher efficiency. apart from the small bypass input capacitor, only a small l-c filter is required at the output. the fixed output version requires only three external power components (c in , c out , and l). the adjustable ver- sion can be programmed with external feedback to any voltage, ranging from 0.6v to near the input voltage. it uses internal mosfets to achieve high efficiency and can generate very low output voltages by using an internal reference of 0.6v. at dropout, the converter duty cycle increases to 100% and the output voltage tracks the input voltage minus the low r ds(on) drop of the p-channel high-side mosfet and the inductor dcr. the internal error amplifier and compensation provides excellent transient response, load and line regulation. internal soft start eliminates any output voltage overshoot when the enable or the input voltage is applied. current mode pwm control slope compensated current mode pwm control provides stable switching and cycle-by-cycle current limit for excellent load and line response with protection of the internal main switch (p-channel mosfet) and synchro- nous rectifier (n-channel mosfet). during normal operation, the internal p-channel mosfet is turned on for a specified time to ramp the inductor current at each rising edge of the internal oscillator, and switched off when the peak inductor current is above the error volt- age. the current comparator, i comp , limits the peak inductor current. when the main switch is off, the syn- chronous rectifier turns on immediately and stays on until either the inductor current starts to reverse, as indicated by the current reversal comparator, i zero , or the beginning of the next clock cycle. functional block diagram r1* r2* r1* r2* pwm logic in v in 2.5v to 5.5v v out c out lx l1 pgnd ovdet osc slope comp softstart ref 0.65v 0.6v 0.6v ain agnd i comp set reset shutdown en fb/out over-temperature and short-circuit protection *the resistor divider r1 + r2 is internally set for the fixed output versions, and is externally set for the adjustable output versions. non-overlap control i zero comp i sense amp
aat1153 2a step-down converter product datasheet 10 1153.2007.11.1.1 www.analogictech.com control loop the aat1153 is a peak current mode step-down con- verter. the current through the p-channel mosfet (high side) is sensed for current loop control, as well as short circuit and overload protection. a slope compensation signal is added to the sensed current to maintain stabil- ity for duty cycles greater than 50%. the peak current mode loop appears as a voltage-programmed current source in parallel with the output capacitor. the output of the voltage error amplifier programs the current mode loop for the necessary peak switch current to force a constant output voltage for all load and line conditions. internal loop compensation terminates the transconduc- tance voltage error amplifier output. for fixed voltage versions, the error amplifier reference voltage is inter- nally set to program the converter output voltage. for the adjustable output, the error amplifier reference is fixed at 0.6v. soft start / enable soft start limits the current surge seen at the input and eliminates output voltage overshoot. the enable pin is active high. when pulled low, the enable input (en) forces the aat1153 into a low-power, non-switching state. the total input current during shutdown is less than 1 a. current limit and over-temperature protection for overload conditions, the peak input current is limited to 3.5a. to minimize power dissipation and stresses under current limit and short-circuit conditions, switch- ing is terminated after entering current limit for a series of pulses. the termination lasts for seven consecutive clock cycles after a current limit has been sensed during a series of four consecutive clock cycles. thermal protection completely disables switching when internal dissipation becomes excessive. the junction over-temperature threshold is 170c with 10c of hys- teresis. once an over-temperature or over-current fault conditions is removed, the output voltage automatically recovers. dropout operation when the battery input voltage decreases near the value of the output voltage, the aat1153 allows the main switch to remain on for more than one switching cycle and increases the duty cycle until it reaches 100%. the duty cycle d of a step-down converter is defined as: 100% d = t on f osc 100% v out v in where t on is the main switch on time and f osc is the oscillator frequency. the output voltage then is the input voltage minus the voltage drop across the main switch and the inductor. at low input supply voltage, the r ds(on) of the p-channel mosfet increases, and the efficiency of the converter decreases. caution must be exercised to ensure the heat dissipated does not exceed the maxi- mum junction temperature of the ic. maximum load current the aat1153 will operate with an input supply voltage as low as 2.5v, however, the maximum load current decreases at lower input voltages due to a large ir drop on the main switch and synchronous rectifier. the slope compensation signal reduces the peak inductor current as a function of the duty cycle to prevent sub-harmonic oscillations at duty cycles greater than 50%. conversely the current limit increases as the duty cycle decreases.
aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 11 www.analogictech.com applications information pgnd pgnd lx lx en in ain agnd fb aat1153-0.6 c1 22f vin 2.5v-5.5v l1 2.2h c3 22pf c2 22f r1 634k r2 316k vout 1.8v, 2a 1 2 3 4 5 7 8 9 10 agnd 6 figure 1: basic application circuit for the adjustable output version. pgnd pgnd lx lx en in ain agnd out aat1153-1.8 c1 22f vin 2.5v-5.5v l1 2.2h c2 22f vout 1.8v, 2a 1 2 3 4 5 7 8 9 10 agnd 6 figure 2: basic application circuit for the fixed output versions. setting the output voltage figure 1 shows the basic application circuit with the aat1153 adjustable output version while figure 2 shows the application circuit with the aat1153 fixed output ver- sion. for applications requiring an adjustable output voltage, the aat1153-0.6 adjustable version can be externally programmed. resistors r1 and r2 in figure 1 program the output to regulate at a voltage higher than 0.6v. to limit the bias current required for the external feedback resistor string while maintaining good noise immunity, the minimum suggested value for r2 is 59k . although a larger value will further reduce quiescent cur- rent, it will also increase the impedance of the feedback node, making it more sensitive to external noise and interference. table 1 summarizes the resistor values for various output voltages with r2 set to either 59k for good noise immunity or 316k for reduced no load input current. the adjustable version of the aat1153, combined with an external feed forward capacitor (c3 in figure 1), delivers enhanced transient response for extreme pulsed load applications. the addition of the feed forward capacitor typically requires a larger output capacitor c2 for stability. the external resistor sets the output voltage according to the following equation: ?? v out = 0.6v 1 + ?? r1 r2 ?? r1 = - 1 r2 ?? v out 0.6v table 1 shows the resistor selection for different output voltage settings. v out (v) r2 = 59k r1 (k ) r2 = 316k r1 (k ) 0.8 19.6 105 0.9 29.4 158 1.0 39.2 210 1.1 49.9 261 1.2 59.0 316 1.3 68.1 365 1.4 78.7 422 1.5 88.7 475 1.8 118 634 1.85 124 655 2.0 137 732 2.5 187 1000 3.3 267 1430 table 1: resistor selections for different output voltage settings (standard 1% resistors substituted for calculated values). inductor selection for most designs, the aat1153 operates with inductor values of 1 h to 4.7 h. low inductance values are physically smaller but require faster switching, which results in some efficiency loss. the inductor value can be derived from the following equation: v out (v in - v out ) v in i l f osc l = where i l is inductor ripple current. large value induc- tors lower ripple current and small value inductors result in high ripple currents. choose inductor ripple current approximately 30% of the maximum load current 2a, or i l = 600m a
aat1153 2a step-down converter product datasheet 12 1153.2007.11.1.1 www.analogictech.com for output voltages above 2.0v, when light-load effi- ciency is important, the minimum recommended induc- tor is 2.2 h. manufacturer?s specifications list both the inductor dc current rating, which is a thermal limitation, and the peak current rating, which is determined by the satura- tion characteristics. the inductor should not show any appreciable saturation under normal load conditions. some inductors may meet the peak and average current ratings yet result in excessive losses due to a high dcr. always consider the losses associated with the dcr and its effect on the total converter efficiency when selecting an inductor. for optimum voltage-positioning load tran- sients, choose an inductor with dc series resistance in the 20m to 100m range. for higher efficiency at heavy loads (above 200ma), or minimal load regulation (but some transient overshoot), the resistance should be kept below 100m . the dc current rating of the induc- tor should be at least equal to the maximum load cur- rent plus half the ripple current to prevent core satura- tion (2a + 600ma). table 2 lists some typical surface mount inductors that meet target applications for the aat1153. for example, the 2.2 h cdrh5d16-2r2 inductor select- ed from sumida has a 28.7m dcr and a 3.0adc cur- rent rating. at full load, the inductor dc loss is 57mw which gives a 1.6% loss in efficiency for a 1200ma, 1.8v output. slope compensation the aat1153 step-down converter uses peak current mode control with slope compensation for stability when duty cycles are greater than 50%. the slope compensa- tion is set to maintain stability with lower value inductors which provide better overall efficiency. the output induc- tor value must be selected so the inductor current down slope meets the internal slope compensation require- ments. as an example, the value of the slope compensa- tion is set to 1a/ s which is large enough to guarantee stability when using a 2.2 h inductor for all output volt- age levels from 0.6v to 3.3v. the worst case external current slope (m) using the 2.2 h inductor is when v out = 3.3v and is: v out l m = = = 1.5a/s 3.3 2.2 to keep the power supply stable when the duty cycle is above 50%, the internal slope compensation (ma) should be: 1 2 m a m = 0.75a/s therefore, to guarantee current loop stability, the slope of the compensation ramp must be greater than one-half of the down slope of the current waveform. so the inter- nal slope compensated value of 1a/ s will guarantee stability using a 2.2 h inductor value for all output volt- ages from 0.6v to 3.3v. input capacitor selection the input capacitor reduces the surge current drawn from the input and switching noise from the device. the input capacitor impedance at the switching frequency should be less than the input source impedance to pre- vent high frequency switching current passing to the input. the calculated value varies with input voltage and is a maximum when v in is double the output voltage. ?? 1 - ?? v o v in c in = v o v in ?? - esr f s ?? v pp i o c in(min) = 1 ?? - esr 4 f s ?? v pp i o a low esr input capacitor sized for maximum rms cur- rent must be used. ceramic capacitors with x5r or x7r dielectrics are highly recommended because of their low esr and small temperature coefficients. a 22 f ceram- ic capacitor for most applications is sufficient. a large value may be used for improved input voltage filtering. the maximum input capacitor rms current is: ?? i rms = i o 1 - ?? v o v in v o v in
aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 13 www.analogictech.com the input capacitor rms ripple current varies with the input and output voltage and will always be less than or equal to half of the total dc load current. 1 rms(max) i i o 2 = to minimize stray inductance, the capacitor should be placed as closely as possible to the ic. this keeps the high frequency content of the input current localized, minimizing emi and input voltage ripple. the proper placement of the input capacitor (c1) can be seen in the evaluation board layout in figures 3 and 4. a laboratory test set-up typically consists of two long wires running from the bench power supply to the evalu- ation board input voltage pins. the inductance of these wires, along with the low-esr ceramic input capacitor, can create a high q network that may affect converter performance. this problem often becomes apparent in the form of excessive ringing in the output voltage dur- ing load transients. errors in the loop phase and gain measurements can also result. since the inductance of a short pcb trace feeding the input voltage is significantly lower than the power leads from the bench power supply, most applications do not exhibit this problem. in applications where the input power source lead induc- tance cannot be reduced to a level that does not affect the converter performance, a high esr tantalum or alu- minum electrolytic should be placed in parallel with the low esr, esl bypass ceramic. this dampens the high q network and stabilizes the system. output capacitor selection the function of output capacitance is to store energy to attempt to maintain a constant voltage. the energy is stored in the capacitor?s electric field due to the voltage applied. the value of output capacitance is generally selected to limit output voltage ripple to the level required by the specification. since the ripple current in the output induc- tor is usually determined by l, v out and v in , the series impedance of the capacitor primarily determines the out- put voltage ripple. the three elements of the capacitor that contribute to its impedance (and output voltage ripple) are equivalent series resistance (esr), equivalent series inductance (esl), and capacitance (c). the output voltage droop due to a load transient is dominated by the capacitance of the ceramic output capacitor. during a step increase in load current, the ceramic output capacitor alone supplies the load current until the loop responds. within three switching cycles, the loop responds and the inductor current increases to match the load current demand. the relationship of the output voltage droop during the three switching cycles to the output capacitance can be estimated by: c out = 3 i load v droop f s in many practical designs, to get the required esr, a capacitor with much more capacitance than is needed must be selected. for both continuous or discontinuous inductor current mode operation, the esr of the c out needed to limit the ripple to ? v o , v peak-to-peak is: esr v o i l ripple current flowing through a capacitor?s esr causes power dissipation in the capacitor. this power dissipation causes a temperature increase internal to the capacitor. excessive temperature can seriously shorten the expect- ed life of a capacitor. capacitors have ripple current rat- ings that are dependent on ambient temperature and should not be exceeded. the output capacitor ripple cur- rent is the inductor current, i l , minus the output current, i o . the rms value of the ripple current flowing in the output capacitance (continuous inductor current mode operation) is given by: 3 6 rms i= i l = i l 0.289 esl can be a problem by causing ringing in the low megahertz region but can be controlled by choosing low esl capacitors, limiting lead length (pcb and capacitor), and replacing one large device with several smaller ones connected in parallel.
aat1153 2a step-down converter product datasheet 14 1153.2007.11.1.1 www.analogictech.com aat1153 2a step-down converter product datasheet 14 1153.2007.11.1.1 www.analogictech.com in conclusion, in order to meet the requirement of out- put voltage ripple small and regulation loop stability, ceramic capacitors with x5r or x7r dielectrics are rec- ommended due to their low esr and high ripple current ratings. the output ripple v out is determined by: v out (v in - v out ) v in f osc l 1 8 f osc c out v out esr + ? ? ? ? a 22 f ceramic capacitor can satisfy most applications. thermal calculations there are three types of losses associated with the aat1153 step-down converter: switching losses, con- duction losses, and quiescent current losses. conduction losses are associated with the r ds(on) characteristics of the power output switching devices. switching losses are dominated by the gate charge of the power output switching devices. at full load, assuming continuous con- duction mode (ccm), a simplified form of the losses is given by: p total i o 2 (r dson(hs) v o + r dson(ls) [v in - v o ]) v in = + (t sw f i o + i q ) v in i q is the step-down converter quiescent current. the term t sw is used to estimate the full load step-down con- verter switching losses. for the condition where the step-down converter is in dropout at 100% duty cycle, the total device dissipation reduces to: p total = i o 2 r dson(hs) + i q v in since r ds(on) , quiescent current, and switching losses all vary with input voltage, the total losses should be inves- tigated over the complete input voltage range. given the total losses, the maximum junction temperature can be derived from the ja for the dfn-10 package which is 45c/w. t j(max) = p total ja + t amb layout guidance when laying out the pc board, the following layout guideline should be followed to ensure proper operation of the aat1153: 1. the exposed pad (ep) must be reliably soldered to the gnd plane. a pgnd pad below ep is strongly recommended. 2. the power traces, including the gnd trace, the lx trace and the in trace should be kept short, direct and wide to allow large current flow. the l1 connec- tion to the lx pins should be as short as possible. use several via pads when routing between layers. 3. the input capacitor (c1) should connect as closely as possible to in (pin 2) and agnd (pins 4 and 6) to get good power filtering. 4. keep the switching node, lx (pins 7 and 8) away from the sensitive fb/out node. 5. the feedback trace or out pin (pin 2) should be separate from any power trace and connect as closely as possible to the load point. sensing along a high-current load trace will degrade dc load regu- lation. if external feedback resistors are used, they should be placed as closely as possible to the fb pin (pin 5) to minimize the length of the high impedance feedback trace. 6. the output capacitor c2 and l1 should be connected as closely as possible. the connection of l1 to the lx pin should be as short as possible and there should not be any signal lines under the inductor. 7. the resistance of the trace from the load return to pgnd should be kept to a minimum. this will help to minimize any error in dc regulation due to differ- ences in the potential of the internal signal ground and the power ground. figures 4, 5 and 6 show an example of a layout with 4 layers. the internal 2 layers are sgnd and pgnd.
aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 15 www.analogictech.com aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 15 www.analogictech.com manufacturer part number inductance ( h) max dc current (a) dcr (m ) size lxwxh (mm) type sumida cdrh5d16 2.2 3.0 28.7 5.8x5.8x1.8 shielded sumida 3.3 2.6 35.6 sumida cdrh8d28 4.7 3.4 19 8.3x8.3x3.0 shielded coiltronics sd53 2.0 3.3 23 5.2x5.2x3.0 shielded coiltronics 3.3 2.6 29 coiltronics 4.7 2.1 39 manufacturer part number value voltage (v) temp. co. case murata grm219r60j106ke19 10 f 6.3 x5r 0805 murata grm21br60j226me39 22 f 6.3 x5r 0805 murata grm1551x1e220jz01b 22pf 25 jis 0402 table 2: suggested component selection information. 2. 5v ~ 5.5v en 1 pgnd 10 u1 aat1153 in 2 ain 3 4 agnd 5 fb pgnd lx lx agnd 9 8 7 6 ep 11 vin l1 2. 2h r2a 316k r1 316k c2 22f vout c3 22pf 1 2 3 5 4 6 78 r2b 634k r2c 1m r2d 1.43m 1.2v, 1.8v, 2.5v, 3.3v c1 22f pgnd jp1 jp3 jp2 sgnd sgnd sgnd sgnd pgnd jp2_1-2: 1.2v; jp2_3-4: 1.8v; jp2_5-6: 2.5v; jp2_7-8: 3.3v. sgnd l1: cdrh5d16-2r2nc c1, c2: grm21br60j226me39 sw figure 3: aat1153 adjustable voltage version recommended evaluation board schematic.
aat1153 2a step-down converter product datasheet 16 1153.2007.11.1.1 www.analogictech.com aat1153 2a step-down converter product datasheet 16 1153.2007.11.1.1 www.analogictech.com figure 4: aat1153 evaluation figure 5: exploded view of aat1153 board component side layout. evaluation board component side layout. figure 6: aat1153 evaluation board solder side layout.
aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 17 www.analogictech.com aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 17 www.analogictech.com step-down converter design example specifications v o = 1.8v @ 2a v in = 2.7v to 4.2v (3.6v nominal) f s = 1.2mhz transient droop = 200mv ? v o = 50mv 1.8v output inductor v out (v in(max) - v out ) v in(max) ? i l ? f osc 1.8 (4.2 - 1.8) 4.2 ? 0.6 1.2 10 6 l = = = 1.4h i l = 30% ? i o = 0.3 2 = 600ma for sumida 2.2 h inductor (cdrh2d14) with dcr 75m , the ? i l should be v o l v o v in 0.395 2 i l = ? 1 - t = 395ma i pkl = i o + i l = 2 + = 2.2a 2 p l = i o 2 ? dcr = 2 2 ? 0.0287 = 114.8mw ? ? ? ? 1.8v output capacitor 3 i load v droop f s 3 1.2 0.2 1.2 10 6 c out = = = 25f; use 22f esr = = 0.13 v o i l 0.05 0.395 select a 22 f, 10m esr ceramic capacitor to meet the ripple 50mv requirement. v out (v in - v out ) v in f osc l 1 8 f osc c out v out esr + ? ? ? ? 1.8 (4.2 - 1.8) 4.2 1.2 10 6 2.2 10 -6 1 8 1.2 10 6 22 10 -6 = 0.01 + = 5.7mv ? ? ? ? i rms = i l 0.289 = 0.395 0.289 = 114marms p cout = esr i rms 2 = 0.01 1 2 = 10mw
aat1153 2a step-down converter product datasheet 18 1153.2007.11.1.1 www.analogictech.com aat1153 2a step-down converter product datasheet 18 1153.2007.11.1.1 www.analogictech.com input capacitor input ripple v pp = 25mv c in(min) = = = 13.9f; use 22f 1 ?? - esr 4 f s ?? v pp i o 1 ?? - 0.01 4 1.2 10 6 ?? 0.025 2 i o rms i p cin = esr i rms 2 = 0.01 1 2 = 10mw 2 2 2 = = = 1arms aat1153 losses p total = i o 2 r ds(on)p d + i o 2 r ds(on)n (1 - d) + (t sw f s i o ) v in = 2 2 0.135 + 2 2 0.095 1 - 1.8 4.2 + (5 10 -9 1.2 10 6 2) 4.2 = 498.9mw 1.8 4.2 ?? ??
aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 19 www.analogictech.com aat1153 2a step-down converter product datasheet 1153.2007.11.1.1 19 www.analogictech.com ordering information output voltage package marking 1 part number (tape and reel) 2 adj. 0.6v to v in tdfn33-10 zsxyy aat1153ide-0.6-t1 fixed 1.8v tdfn33-10 ztxyy aat1153ide-1.8-t1 all analogictech products are offered in pb-free packaging. the term pb-free means semiconductor products that are in compliance with current rohs standards, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. for more information, please visit our website at http://www.analogictech.com/pbfree. package information 3 tdfn33-10 2.000 all dimensions in millimeters. 1. xyy = assembly and date code. 2. sample stock is generally held on all part numbers listed in bold. 3. the leadless package family, which includes qfn, tqfn, dfn, tdfn and stdfn, has exposed copper (unplated) at the end of the lead terminals due to the manufacturing process. a solder fillet at the exposed copper edge cannot be guaranteed and is not required to ensure a proper bottom solder connection.
aat1153 2a step-down converter product datasheet 20 1153.2007.11.1.1 www.analogictech.com aat1153 2a step-down converter product datasheet 20 1153.2007.11.1.1 www.analogictech.com advanced analogic technologies, inc. 3230 scott boulevard, santa clara, ca 95054 phone (408) 737-4600 fax (408) 737-4611 ? advanced analogic technologies, inc. analogictech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an analogictech pr oduct. no circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. analogictech reserves the right to make changes to their products or speci cations or to discontinue any product or service without notice. except as provided in analogictech?s terms and conditions of sale, analogictech assumes no liability whatsoever, and analogictech disclaims any express or implied warranty re lating to the sale and/or use of analogictech products including liability or warranties relating to tness for a particular purpose, merchantability, or infringement of any patent, copyright or other intellectual property right . in order to minimize risks associated with the customer?s applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards. testing and other quality control techniques are utilized to the extent analogictech deems necessary to support this warranty. speci c testing of all parameters of each device is not necessarily performed. analogictech and the analogictech logo are trademarks of advanced analogic technologies incorporated. all other brand and product names appearing in this document are registered trademarks or trademarks of their respective holders.

▲Up To Search▲

Price & Availability of AAT1153IDE-06-T1

	To Download AAT1153IDE-06-T1 Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .